Lecture 08 State Feedback Controller Design

# Lecture 08 State Feedback Controller Design

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## Lecture 08 State Feedback Controller Design

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1. Lecture 08 State Feedback Controller Design 8.1 State Feedback and Stabilization 8.2 Full-Order Observer Design 8.3 Separation Principle 8.4 Reduced-Order Observer 8.5 State Feedback Control Design with Integrator Modern Control Systems

2. State Feedback and Stabilization Stabilization by State Feedback: Regulator Case Plant: State Feedback Law: Closed-Loop System: Theorem Given Controllable There exists a state feedback matrix, F, such that Modern Control Systems

3. D B C A F State Feedback System (Regulator Case) Modern Control Systems

5. Suppose the desired characteristic polynomial (8.2) Comparing (8.1) and (8.2), we have (8.3) Modern Control Systems

6. State Feedback: General Case (Non-Zero Input Case) D B C A F State Feedback Control System Modern Control Systems

7. State Feedback Design with Transformation to Controllable Form Controllable From: Modern Control Systems

8. Transform to Controllable Form Coordinate Transform Matrix Controllable Form: Modern Control Systems

9. Example (A, B) is in controllable from, we can derive the state feedback gain from eq. (8.3) Modern Control Systems

10. Obtain the State Feedback Matrix by Comparing Coefficients Plant: State Feedback: Closed Loop System: Char. Equation: Suppose that the system is controllable, i.e. Modern Control Systems

11. Then, for any desired pole locations: We can obtain the desired char. polynomial By controllability, there exists a state feedback matrix K, such that (8.4) From (8.4), we can solve for the state feedback gain K. Modern Control Systems

12. Example Plant: State Feedback: Fig. State Feedback Design Example Modern Control Systems

13. Spec. for Step Response: Percent Overshoot 5%, Settling Rise time 5 sec. Desired pole locations: From (8.4), we get (8.5) By comparing coefficients on the both sides of 8.5), we obtain Modern Control Systems

14. Simulation Results Fig. Step response of above example Modern Control Systems

15. Ackermann Formula for SISO Systems Plant: State Feedback: The Matrix Polynomial Then the state feedback gain matrix is Modern Control Systems

16. Steady State Error Error Variable Lapalce Transform of the Error Variable From (3.6) By Final Value Theorem Modern Control Systems

17. Full-Order Observer Design Full-Order Observer Plant: Suppose is the observer state L: Observer gain Estimation error: Error Dynamics Equation: Modern Control Systems

18. C B A + L C B A Hence if all the eigenvalues of (A-LC) lie in LHP, then the error system is asy. stable and Fig. Full-Order Observer Modern Control Systems

19. By duality between controllable from and obeservable form we have the following theorem. Theorem Given Observable There exists a observer matrix, L, such that Modern Control Systems

20. The eigenvalues of can be assigned arbitrarily by proper choice of K. Since have same eigenvalues, if we choose then the eigenvalues of (A-LC) can be arbitrarily assigned. Modern Control Systems

21. Separation Principle Plant: State Feedback Law using estimated state: State Equation: (8.6) Observer: Error Dynamics: (8.7) Modern Control Systems

22. Separation Principle (Cont.) From (8.6) and (8.7), we obtain the overall state equation (8.8) Eigenvalues of the overall state equation (7.17) (8.9) Equation (8.9) tells us that the eigenvalues of the observer-based state feedback system is consisted of eigenvalues of (A-BF) and (A-LC). Hence, the design of state feedback and observer gain can be done independently. Modern Control Systems

23. Observer-Based Control System Plant: Observer： State Feedback Law: Modern Control Systems

24. C B A L C B A K Fig. Observer-based control system Modern Control Systems

25. C B A L C B A K Fig. Observer-based control system with compensating gain Modern Control Systems

26. Reduced-Order Observer Design Consider the n-dimensional dynamical equation (8.10a) (8.10b) Here we assume that C has full rank, that is, rank C =q. Then, there exists a coordinate transformation which can be partitioned as (8.11) Modern Control Systems

27. , we have Since (8.12a) (8.12b) which become (8.13a) Plant: (8.13b) where Observer: Observer Modern Control Systems

28. Note that and w are function of known signals u and y. Now if the dynamical equation above is observable, an estimator of can be constructed. Theorem: The pair {A, C} in (8.10) or, equivalently, the pair in (8.12) is observable if and only if the pair in (8.13) is observable. Modern Control Systems

29. Let the estimate of be Such that the eigenvalues of can be arbitrarily assigned by a proper choices of . The substitution of w and into (8.143) yields (8.14) (8.15) To eliminate the term of the derivative of y, by defining (8.16) Modern Control Systems

30. is an estimate of . Using (8.15), then the derivative of (8.16) becomes From (8.15), we see that Define the following matrices Modern Control Systems

31. Reduced-Order Observer: where Modern Control Systems

32. C B A + + Fig. Reduced-Order Observer Modern Control Systems

33. Define Error Variable then we have Modern Control Systems

34. Since the eigenvalues of can be arbitrarily assigned, the rate of e(t) approaching zero or, equivalently, the rate of approaching can be determined by the designer. Now we combine with to form Then from We get Modern Control Systems

35. How to transform state equation to the form of (8.11) Consider the n-dimensional dynamical equation (8.17a) (8.17b) Here we assume that C has full rank, that is, rank C =q. Define where R is any (n-q)n real constant matrix so that P is nonsingular. Modern Control Systems

36. Compute the inverse of P as where Q1and Q2are nq and n(n-q) matrices. Hence, we have Modern Control Systems

37. Now we transform (8.17) into (8.11), by the equivalence transformation which can be partitioned as Modern Control Systems

38. SISO State Space System Integral Control: Augmented Plant: Modern Control Systems

39. State Feedback Control Design with Integrator Closed-Loop System: Modern Control Systems

40. Block diagram of the integral control system C B A K Fig.Block diagram of the integral control system Modern Control Systems

41. Example Spec. for Step Response: Percent Overshoot 10%, Settling time 0.5 sec. State Feedback Design: Modern Control Systems

42. From the steady state analysis in Sec. 3.4 Modern Control Systems

43. State Feedback Design with Error Integrator: Closed-Loop System: (8.18) Modern Control Systems

44. From (8.18), we get the char. eq. of the closed-loop system is (8.19) The desired char. eq. of the closed-loop system is (8.20) By comparing coefficients on left hand sides of (8.19) and (8.20), we obtain Modern Control Systems

45. Closed-Loop System: Final Value Theorem Steady State Error Modern Control Systems